Circuit and method for limiting power to a load

ABSTRACT

A circuit and method for limiting the power supplied to a load are provided. The circuit and method prevent power supplied to the load from exceeding a power threshold for a programmable amount of time specified in a timer. The circuit includes a voltage controlled current source coupled to the load. A current multiplier divider is coupled to the voltage controlled current source and a timer is coupled to the load. A comparator with an adaptive threshold is coupled to the current multiplier divider and the input for controlling the timer to limit the power supplied to the load.

FIELD OF THE INVENTION

The present invention relates generally to power controllers, and more particularly, to a power controller having an adaptive trip threshold for limiting the power supplied to a load.

BACKGROUND INFORMATION

Power controllers have been provided to limit the power delivered to a load, thereby protecting it from thermal failure or other damage. See, for example, U.S. Pat. No. 6,141,197, providing a smart circuit breaker for residential use, U.S. Pat. No. 6,836,099, providing a power controller for real-time monitoring and adjustment of power usage by the load, U.S. Pat. No. 6,704,181, providing an adaptive power controller that dynamically controls the power based on information received from the load, and U.S. Pat. No. 6,122,180, providing a constant power controller for maintaining a constant power to the load.

In particular, constant power controllers monitor the power delivered to the load such that the power may not exceed a predetermined power level for some programmable amount of time. Such power level may be the constant maximum value permitted by the load and set by the load manufacturer to comply with its safety restrictions. In typical implementations, an adaptive trip threshold may be used to indicate when to trip off power to the load. Usually it is desirable to implement the adaptive trip threshold transfer function with accuracy less than +/−2%. Realization of such transfer function prevents excessive losses of power without violating the safety restrictions of the load.

There remains, however, a need to implement this transfer function with higher accuracy and with a relatively simple power controller circuit.

SUMMARY OF THE INVENTION

In view of the foregoing, the present invention provides a power controller circuit for use with an input voltage to limit the power supplied to a load. The power controller circuit has an input adapted to receive the input voltage and includes a voltage controlled current source coupled to the load. A current multiplier divider is coupled to the voltage controlled current source and a timer is coupled to the load. A comparator is coupled to the current multiplier divider and the input for controlling the timer to limit the power supplied to the load.

DESCRIPTION OF THE DRAWINGS

The accompanying drawings, which are somewhat schematic in some instances and are incorporated in and form a part of this specification, illustrate several embodiments of the invention and, together with the description, serve to explain the principles of the invention.

FIG. 1 is a schematic diagram of a power controller circuit in accordance with the present invention.

FIG. 2 is a schematic diagram of the current multiplier divider incorporated in the power controller circuit of FIG. 1.

FIG. 3 is a graph of an adaptive trip threshold transfer function implemented according to the present invention.

FIG. 4 is a flow chart showing exemplary steps for controlling power supplied to a load in accordance with the present invention.

DETAILED DESCRIPTION OF EMBODIMENTS OF THE INVENTION

The method of the present invention for controlling the power delivered to a load can be performed with a power controller circuit of the type shown in FIGS. 1-2 having the exemplary transfer function shown in FIG. 3. Power controller circuit 100 is adapted to sense a voltage across the load V_(load) to generate an output voltage V_(out) such that the power delivered to the load may not exceed a predetermined power level for some programmable amount of time.

Power controller circuit 100 may be implemented with an adaptive trip threshold that may be determined by: $\begin{matrix} {V_{TH} = {\frac{Power}{V_{load}} \times R_{SENS}}} & (1) \end{matrix}$ where Power is the constant maximum value permitted by the load and set by the load manufacturer to comply with its safety restrictions, V_(load) is the voltage directly across the load, R_(SENS) is a sensor resistor to monitor the output current and V_(TH) is the adaptive trip threshold.

Power controller circuit 100, for use with voltage V_(load), implements an adaptive voltage threshold to limit the power supplied to a load. Power controller circuit 100 includes highly linear voltage controlled current source 105 coupled to the load via a voltage divider formed by resistors 110 and 115 for generating a current that is input into precision current mirror 120. Precision current mirror 120 generates a current equal to its input current. This current is then input into current multiplier divider 125 coupled between precision current mirror 120 and biasing circuit 130. Biasing circuit 130 has bandgap voltage reference 135 coupled to current reference 140 and current mirror 145 to generate a reference current that is fed into current multiplier divider 125. The output of current multiplier divider 125 is coupled to current controlled voltage source 150 for generating the adaptive voltage threshold.

Power controller circuit 100 also includes means for comparing the adaptive voltage threshold with a sensor voltage developed across sensor resistor 155 from the input voltage and the current across the load. The means for comparing may include differential comparator 160 coupled to current controlled voltage source 150 or any other equivalent circuit capable of performing a comparison between two voltages.

Power controller circuit 100 further includes means for limiting the power supplied to the load if the sensor voltage exceeds the adaptive voltage threshold. The means for limiting the power may include programmable over current timer 165 coupled to differential comparator 160 and switch 170 coupled between programmable over current timer 165 and the load or any other equivalent circuit capable of limiting the power supplied to the load in the event the sensor voltage is above the adaptive voltage threshold.

Additional external components may include bypass capacitor C_(bypass) 175 coupled to the load and power NFET 180 coupled between sensor resistor 155 and the load. Gate current source 185 is coupled to NFET 180 and switch 170 for ensuring a minimum drain-to-source voltage across NFET 180.

Operation of power controller circuit 100 is as follows. The voltage divider formed of resistors 110 and 115 generates an output voltage V_(out) given by: $\begin{matrix} {V_{out} = {\frac{R_{1}}{R_{1} + R_{2}} \times V_{load}}} & (2) \end{matrix}$ where N is the attenuation factor: $\begin{matrix} {\frac{R_{1}}{R_{1} + R_{2}} = N} & (3) \end{matrix}$

The output voltage V_(out) given by Equation (2) above is applied as an input to highly linear voltage controlled current source (“VCCS”) 105. The output current of VCCS 105, denoted by I_(VCCS), is proportional to the input current and consequently, strictly proportional to the output voltage directly developed on the load terminal, i.e., V_(out). This current, I_(VCCS), is then applied as an input to precision current mirror 120, which, in turn, generates a regulated current denoted by I_(B) that may be equal to the input current I_(VCCS).

The current I_(B) generated by precision current mirror 120 is then input into current multiplier divider 125. Current multiplier divider 125, shown in FIG. 2, receives two other input currents as illustrated: I_(A) and I_(C), which are two equal constant currents derived from the reference current I_(REF) generated by biasing circuit 130. Biasing circuit 130 may includes bandgap voltage reference 135, current reference 140, and current mirror 145 to generate constant current reference I_(REF).

Current multiplier divider 125 performs arithmetic functions with four bipolar junction transistors Q1-Q4 (transistors 200, 205, 210 and 215) coupled to V_(cc), current sources 220, 225 and 230 coupled to transistors 200, 205, and 215, respectively, amplifier 235 coupled between transistors 205 and 210, PMOS transistor 240 coupled to amplifier 235, and NMOS transistors 245 and 250 coupled to PMOS transistor 240.

To understand how arithmetic functions are performed by current multiplier divider 125, it is necessary to consider the operation of transistors 200, 205, 210, and 215 with the following operating equations: $\begin{matrix} {V_{be} = {V_{t} \times {\ln\left( \frac{I_{e}}{I_{s}} \right)}}} & (4) \\ {I_{e} = {I_{s} \times {\mathbb{e}}^{(\frac{V_{be}}{V_{t}})}}} & (5) \end{matrix}$ where V_(be) is the base-emitter voltage, V_(t) is the thermal voltage, I_(e) is the emitter current, and I_(s) is the saturation current.

If V_(e3)=V_(e4), with V_(e3) being the emitter voltage through transistor Q3 (205) and V_(e4) being the emitter voltage through transistor Q4 (210), it follows that: V _(be1) +V _(be3) =V _(be2) +V _(be4)  (6) Applying Equation (4) into Equation (6) results in: $\begin{matrix} {{\left\lbrack {V_{t} \times {\ln\left( \frac{I_{e\quad 1}}{I_{s}} \right)}} \right\rbrack + \left\lbrack {V_{t} \times {\ln\left( \frac{I_{e\quad 3}}{I_{s}} \right)}} \right\rbrack} = {\left\lbrack {V_{t} \times {\ln\left( \frac{I_{e\quad 2}}{I_{s}} \right)}} \right\rbrack + \left\lbrack {V_{t} \times {\ln\left( \frac{I_{e\quad 4}}{I_{s}} \right)}} \right\rbrack}} & (7) \end{matrix}$

Eliminating the thermal voltage V_(t) and operating on the logarithms to eliminate the saturation current I_(s) from Equation (7) above results in: ln(I _(e1) ×I _(e3))=ln(I _(e2) ×I _(e4))  (8)

Removing the logarithms from Equation (8) results in: I _(e1) ×I _(e3) =I _(e2) ×I _(e4)  (9)

With V₊=V⁻, I_(e2)=I₂, I_(e3)=I₃ and I_(e4)=I₄=I_(out), Equation (9) above may be rewritten as: $\begin{matrix} {I_{out} = \frac{I_{1} \times I_{3}}{I_{2}}} & (10) \end{matrix}$

Equation (10) above therefore represents the arithmetic operations performed by current multiplier divider 125, that is, current multiplier divider 125 receives three input currents and outputs a current that is the result of the multiplication of two of the input currents divided by the third current. The output of current multiplier divider 125 may thus be given by: $\begin{matrix} {I_{TH} = \frac{I_{C} \times I_{A}}{I_{B}}} & (11) \end{matrix}$ With I_(A) and I_(C) equal to I_(REF), that is, with I_(A)=I_(C)=I_(REF), Equation (11) above may be rewritten as: $\begin{matrix} {I_{TH} = \frac{I_{REF}^{2}}{I_{B}}} & (12) \end{matrix}$

Applying this current, I_(TH), to current controlled voltage source 150 therefore results in the following Equation: $\begin{matrix} {V_{TH} = {{I_{TH} \times R_{TH}} = {\frac{I_{REF}^{2}}{I_{B}} \times R_{TH}}}} & (13) \end{matrix}$ With current mirror 120 being a precision current mirror and I_(B) being approximately equal to I_(VCCS), Equation (13) may be rewritten as: $\begin{matrix} {V_{TH} = {\frac{I_{REF}^{2}}{I_{VCCS}} \times R_{TH}}} & (14) \end{matrix}$ where V_(TH) is the adaptive voltage threshold generated by current controlled voltage source 150 and R_(TH) is the equivalent input resistance of differential comparator circuit 153. For practical considerations, in order to avoid threshold shifting due to bias currents, it is recommended that R_(TH) be no higher than 2-2.5 kilo-ohms.

It is appreciated that Equation (14) above may be compared to Equation (1) above, with the constant Power represented by the constant current I_(REF) ², the voltage across the load V_(load) represented by the current I_(VCCS), which is a function of V_(load), and R_(SENS) represented by R_(TH).

To satisfy Equation (1) with comparable Equation (14) above with the given I_(REF) current and R_(TH) resistance, it is necessary to determine the relationship between the current I_(VCCS) and the voltage V_(load). For two different voltages V_(load) _(—) ₁ and V_(load) _(—) ₂ and corresponding output voltages V_(out) _(—) ₁ and V_(out) _(—) ₂, the slope G_(M) of VCCS 105 may be expressed as: $\begin{matrix} {G_{M} = \frac{I_{{VCCS\_}1} - I_{{VCCS\_}2}}{V_{{out\_}1} - V_{{out\_}2}}} & (15) \end{matrix}$ With V_(out)=N×V_(in) as in Equation (2) above, Equation (15) may be rewritten as: $\begin{matrix} {G_{M} = {\frac{I_{{VCCS\_}1} - I_{{VCCS\_}2}}{V_{{load\_}1} - V_{{load\_}2}} \times \frac{1}{N}}} & (16) \end{matrix}$

Since G_(M) is the slope of VCCS 105, it follows that resistor R_(VCCS) must be chosen as follows for Equation (14) to hold: $\begin{matrix} {R_{VCCS} = {\frac{1}{G_{M}} \times \frac{1}{N}}} & (17) \end{matrix}$

With the adaptive voltage threshold V_(TH) determined by Equation (14), differential comparator 160 compares it to a sensor voltage, denoted by V_(SENS), across sensor resistor R_(SENS) (155). This sensor voltage V_(SENS) may be expressed as: V _(SENS) =I _(LOAD) ×R _(SENS)  (18) so that: V _(out) =V _(in) I _(LOAD)×(R _(SENS) +R _(DS))  (19) where R_(DS) is the drain-source resistance of external NFET 180.

To insure a minimum RDS across external NFET 180, gate current source 185 charges the gate of external NFET 180 with its slew rate so that: $\begin{matrix} {\frac{\mathbb{d}v}{\mathbb{d}t} = \frac{I_{gate}}{C_{gate}}} & (20) \end{matrix}$

The sensor voltage V_(SENS) is then compared with the adaptive voltage threshold V_(TH) with differential comparator 160. As long as V_(SENS)≦V_(TH), differential comparator 160 may not trip off, that is, power controller circuit 100 may provide practically the full scale of the input voltage V_(in) to the load.

However, if for any reason V_(SENS)≧V_(TH), differential comparator 160 may trip off and trigger programmable timer 165. If this occurs longer than a given predetermined time period, programmable timer 165 activates switch 170, which in turn, immediately disconnects the load to protect the load from thermal failure or other damage.

It is then appreciated that, as described above, power controller circuit 100 continuously measures the power to be delivered across the load by monitoring the current across the load I_(LOAD) and the output voltage V_(out) and comparing the sensor voltage V_(SENS) to the adaptive voltage threshold V_(TH). It is also appreciated that the adaptive voltage threshold V_(TH) may be considered a nonlinear function of the input and output voltages.

Using current multiplier divider 125 in power controller circuit 100 shown in FIG. 1 results in an adaptive trip threshold transfer function that is accurate and simple to implement. An exemplary graph of such adaptive trip threshold transfer function is illustrated in FIG. 3. Graph 300 shows the changes in value of adaptive voltage threshold V_(TH) with changes in value of the voltage V_(load). In one exemplary embodiment with Power=240 Volts-Amperes and R_(SENS)=three mili-ohms, the adaptive voltage threshold changes from approximately 68.6 to 51.4 mili-volts. Realization of such transfer function prevents excessive losses of power without violating the safety restrictions of the load.

The method of the present invention for implementing this transfer function with the power controller circuit 100 of FIG. 1 is illustrated in a flow chart in FIG. 4. After generating a sensor voltage V_(SENS) across the sensor resistor R_(SENS) at step 405 and coupling voltage-controlled current source 160 to the input and the load at step 410 to generate current I_(VCCS) at step 415, the adaptive voltage threshold V_(TH) is generated at step 420. The sensor voltage V_(SENS) is compared to the adaptive voltage threshold V_(TH) at step 425, and if the comparison shows that V_(SENS) is at least equal to or above V_(TH), programmable timer 145 is triggered at step 430. If timer 145 is activated for more than a given predetermined time (step 435), the load is disconnected at step 445 to prevent the load from suffering thermal failure or other damage. Otherwise, the input voltage V_(in) is supplied to the load at step 440.

It is appreciated that the steps shown in FIG. 4 are for illustration purposes only. Additional steps may be inserted therein without deviating from the principles and embodiments of the present invention.

The foregoing descriptions of specific embodiments and best mode of the present invention have been presented for purposes of illustration and description only. They are not intended to be exhaustive or to limit the invention to the precise forms disclosed. Specific features of the invention are shown in some drawings and not in others, for purposes of convenience only, and any feature may be combined with other features in accordance with the invention. Steps of the described processes may be reordered or combined, and other steps may be included.

The embodiments were chosen and described in order to best explain the principles of the invention and its practical application, to thereby enable others skilled in the art to best utilize the invention and various embodiments with various modifications as are suited to the particular use contemplated. Further variations of the invention will be apparent to one skilled in the art in light of this disclosure and such variations are intended to fall within the scope of the appended claims and their equivalents. 

1. A circuit for use with an input voltage to limit the power supplied to a load, comprising an input adapted to receive the input voltage, a voltage controlled current source coupled to the load, a current multiplier divider coupled to the voltage controlled current source, a timer coupled to the load and a comparator coupled to the current multiplier divider and the input for controlling the timer to limit the power supplied to the load.
 2. The circuit of claim 1, further comprising a current mirror, the voltage controlled current source being coupled to the current mirror.
 3. The circuit of claim 2, wherein the current mirror is coupled between the voltage controlled current source and the current multiplier divider.
 4. The circuit of claim 1, further comprising a biasing circuit coupled to the current multiplier divider for providing a first input current and a second input current to the current multiplier divider.
 5. The circuit of claim 4, wherein the current multiplier divider provides an output current based upon the first input current, the second input current and the input current provided by the voltage controlled current source.
 6. The circuit of claim 1, wherein the comparator is coupled to a current controlled voltage source to provide a current controlled adaptive voltage threshold as an input to the comparator.
 7. The circuit of claim 6, wherein the comparator includes a differential comparator.
 8. The circuit of claim 7, further comprising a sensor resistor, a bypass capacitor, and a transistor coupled between the input and the load.
 9. The circuit of claim 8, further comprising a voltage gate current source coupled to the transistor.
 10. The circuit of claim 8, wherein the timer is coupled to a switch that turns off power to the load if the voltage across the sensor resistor exceeds the current controlled adaptive voltage threshold for a programmable amount of time.
 11. A circuit for use with an input voltage to limit the power supplied to a load, comprising an input adapted to receive the input voltage, a current controlled voltage source coupled to the input for generating an adaptive voltage threshold, a sensor resistor coupled between the input and the load, means for comparing a voltage across the sensor resistor to the adaptive voltage threshold and means for limiting power supplied to the load if the voltage across the sensor resistor exceeds the adaptive voltage threshold.
 12. The circuit of claim 11, wherein the means for comparing the voltage across the sensor resistor to the adaptive voltage threshold includes a comparator.
 13. The circuit of claim 12, further comprising a timer coupled to the comparator.
 14. The circuit of claim 13, further comprising a switch coupled to the timer for turning off power to the load if the voltage across the sensor resistor exceeds the adaptive voltage threshold for a programmable amount of time.
 15. A method for limiting power supplied to a load, comprising providing an input voltage at an input, generating a sensor voltage across a sensor resistor from the input voltage, generating a current by coupling a voltage controlled current source to the load, controlling a voltage source with the current to generate an adaptive voltage threshold, comparing the sensor voltage to the adaptive voltage threshold, and limiting power to the load if the sensor voltage exceeds the adaptive voltage threshold.
 16. The method of claim 15, wherein the comparing step includes comparing the sensor voltage to the adaptive voltage threshold using a comparator.
 17. The method of claim 16, further comprising turning off power to the load if the sensor voltage exceeds the adaptive voltage threshold for a programmable period of time. 